Hand augmenting spinal manipulator encircling the hand

ABSTRACT

A device for treatment of anterior displacement of the vertebrae fits over the hand of the chiropractor. A groovein a first surface fits over the spinous processes and ridges parallel to the groove engage the transverse processes of the patient&#39;s vertebrae. The device is positioned immediately below the displaced vertebra and the patient is thrust backward. A second surface of the device engages the treatment table and arrests the backward motion of the normal vertebrae. The anteriorly displaced vertebra continues its backward motion, moving back into alignment with its neighbors. This manipulation is ordinarily performed against the chiropractor&#39;s bare hand. This device protects the hand from injury and enhances the performance of the treatment.

This invention relates to apparatus for straightening the spinal column by correcting the anterior displacement of one or more vertebrae and more particularly to apparatus slipped over the hand that is used as a fulcrum or stop by the chiropractor for this purpose that protects the hand from injury during the manipulation.

BACKGROUND OF THE INVENTION

U.S. Pat. No. 4,230,099 teaches a support curved to the normal shape of the spine with a longitudinal groove admitting the spinous processes and a pair of parallel elevations bordering the groove for engaging the transverse processes of the vertebrae.

When a person lies supine upon the support any misalignment of the vertebrae will, according to the inventor, be corrected without medical care or chiropractic manipulation.

In one type of misalignment of the vertebrae, to which the instant invention is directed, one or more vertebrae may be displaced anteriorly relative to adjacent vertebrae. When the displacement, or subluxation, involves many vertebrae, it may be referred to as Pottenger's Saucer because of the dish-like appearance of the back.

U.S. Pat. No. 4,611,581 teaches invasive, i.e. surgical, apparatus for correcting this condition by screws inserted into adjacent bones with pulling forces applied through a common plate that receives the screws and applies forces adjusted by nuts on the screws. The plate pulls the screw and the displaced vertebra in which it is inserted back into alignment with its normally positioned neighbors.

Chiropractors are taught a manipulation of the spine to non-invasively correct this condition. The chiropractor places his first hand on the patient's spine with the upper edge of the hand at the level of the normal vertebra immediately adjacent to the lowest anteriorly displaced vertebra. The chiropractor's second hand thrusts the patient's body weight toward the first hand in a thrusting motion directed backward (from chest to spine) and upward (from feet to head). The backward and upward motion of the spine is stopped by the first hand when it contacts the table on which the patient is lying supine. Because the hand is against the normally positioned vertebrae, but not the anteriorly displaced vertebrae, the motion of the displaced vertebra or vertebrae continue backward, moving back into normal alignment with the adjacent lower vertebrae. The thrust must be upward as well as backward because the facets, or meeting planes, between adjacent vertebrae are not at a ninety degree angle to the axis of the spine but extend upward at a lesser angle.

Each vertebra has a backward projecting, midline spinous process flanked on each side by a laterally projecting transverse process. When the patient is slender, the chiropractor uses the flat hand with the spine positioned between the heel of the hand engaging the transverse processes on a first side of the spinous processes and the metacarpal heads of the hand engaging the transverse processes on a second side of the spinous processes. For medium body types, the fingers are flexed to provXCL 307297

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to digital level shifters and more particularly to CMOS level shifters.

2. Description of the Prior Art

Level shifters typically provide an output signal shifted in voltage level from an input signal voltage level. A wide variety of digital electronic devices employ level shifters to shift the voltage levels at which logic functions are conducted by various circuits within the device. Due to a number of economic and design considerations some circuits such as, for example, timing circuits may employ relatively low voltage levels to represent logical LOW or HIGH signal values while other circuits such as, for example, erasable programmable read-only memories (EPROMs) may require generally higher voltage levels (for example, to inject electrons into a floating gate in order to program the EPROM). Level shifters can provide a suitable interface between circuits operating a different voltage levels thereby obviating the need to design all of the circuits to operate at the same voltage levels. A savings in the total amount of power dissipated by a digital electronic device can be obtained by operating some of the circuits at lower voltage levels.

Level shifters can be configured in a number of different circuits and incorporate several different transistor design technologies. Typically, level shifters incorporating CMOS transistor designs provide a greater savings in power consumption over circuit designs incorporating p-channel transistors, n-channel transistors, or bipolar transistors alone. CMOS level shifters, however, suffer from a relatively slow output signal transition speed which generally limits their operating frequency to the kilohertz region.

One type of prior art CMOS level shifter incorporates two pairs of complementary metal oxide semiconductor transistors with each pair having a first and second transistor of opposite conductivity type connected together and respectively connected to a first and second voltage source. The gates of the p-channel transistors in each pair are bridged by a signal inverter and the gates of the n-channel transistors in each pair are cross connected to the transistor interconnection of the opposing transistor pair. An input signal is provided to the gate of the first pair p-channel transistor and an inverted or non-inverted output signal may be derived from the transistor interconnections of the first and second transistor pairs respectively.

In an initial state, the p-channel transistor of one pair and the n-channel transistor of the opposing pair are in a conducting or "of" state, and the opposite p-channel and n-channel transistors in a non-conducting or "off" state. When the input signal voltage level shifts, the first two transistors will turn off and the other p-channel transistor and opposing transistor pair n-channel transistor will turn on. During the transition, however, the p-channel transistors will switch conducting states more quickly than the n-channel transistors, resulting in the final conducting state p-channel transistor pulling up against the drain of its paired n-channel transistor until the voltage level between the two transistors changes sufficiently to turn on the opposing pair n-channel transistor. This complementary transistor pair transition phase draining characteristic places a severe restriction on the size ratios of the complementary tansistors in each pair and also restricts the operating frequency of the level shifter. Transition phase draining also increases the transient power consumption of the CMOS level shifter.

Thus there exists a need for a faster CMOS level shifter in which transistor pair transition phase draining is minimized.

SUMMARY OF THE INVENTION

The present invention provides a novel CMOS level shifter in which complementary transistor pair transition phase draining is minimized. The present inventive level shifter is therefore able to quickly switch between output signal voltage levels with minimal transient power consumption.

In general terms the circuit, in its several presently preferred embodiments, includes a comlementary MOS transistor pair level shifter with various novel discharging circuits connected to the gates of the cross connected transistors of each complementary pair. The discharging circuits drain a capacitive gate charge present on the cross connected transistors at the onset of signal transition. To minimize transient power consumption, these discharging circuits may be configured to operate only briefly during the onset of output signal transition.

The novel features which are believed to be characteristic of the present invention will be better understood from the following detailed description, considered in connection with the accompanying drawings, wherein various circuits embodying the present invention are described and in which like numbers denote like elements.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a schematic diagram of a generalized circuit embodying the present inventive circuit.

FIG. 2 is a schematic diagram of a preferred embodiment of the present inventive circuit.

FIG. 3 is a schematic diagram of another preferred embodiment of the present inventive circuit.

FIG. 4 is a schematic diagram of still another preferred embodiment of the present inventive circuit.

FIG. 5 is a schematic diagram of yet another preferred embodiment of the present inventive circuit.

DETAILED DESCRPTION OF THE INVENTION

Referring to the figures, and more particularly FIG. 1 thereof, there is shown a generalized schematic diagram of one embodiment of the present inventive level shifter. The level shifter includes a first and second pair of complementary metal oxide semiconductor (CMOS) transistors having p-channel transistors 10, 12 respectively connected to n-channel transistors 14, 16 at nodes 18, 20. The sources of transistors 10, 12 are connected to a first voltage source providing a voltage level V_(DD) and the sources of transistors 14, 16 are connected to a second voltage source providing a voltage level V₂. Typically V₂ is a lower voltage level than V_(DD). A signal inverter 22 is connected across the gates of transistors 10, 12 while the gates of transistors 14, 16 are respectively cross connected to the opposing complementary transistor pair nodes 20, 18. A signal input 24 providing a digital input signal varying between V_(DD) and a voltage level V₁ is applied to the gate of the transistor 10. Typically V₁ is a lower voltage level than V_(DD). An output signal varying between voltage levels V_(DD) and V₂ may be obtained at either of nodes 18 or 20.

In operation, with an input signal at voltage level V_(DD), p-channel transistor 10 and n-channel tansistor 16 will be in a nonconducting or "off" state while the p-channel transistor 12 and n-channel transistor 14 will be in a conducting or "on" state. An output signal obtained from node 20 will be at voltage level V_(DD) and an output signal obtained from node 18 will be inverted at voltage level V₂. When the input signal voltage level shifts from V_(DD) to V₁, transistors 10 and 16 turn on while transistors 12 and 14 turn off. The output signal voltage level at node 20 will now be level shifted to V₂ and the inverted signal output voltage level at node 18 will be level shifted to V_(DD).

At the onset of input signal transition from V_(DD) to V₁, after transistor 10 has turned on and transistor 12 turned off, the gate of the transistor 14 will be floating at approximately V_(DD) due to a capacitive charge remaining on the gate. Transistor 14 may therefore potentially remain on, requiring transistor 10 to pull up against the drain of transistor 14 in order to turn on transistor 16. When transistor 16 turns on, the gate of transistor 14 will drop to V₂ and transistor 14 will turn off. Similarly, at the onset of input signal transition from V₁ back to V_(DD), after transistor 12 has turned on and transistor 10 turned off, the gate of transistor 16 will be floating at approximately V_(DD) due to a capacitive charge remaining on the gate. At this point transistor 16 may potentially remain on requiring transistor 12 to pull up against the drain of transistor 16 in order to turn on transistor 14.

To allow the p-channel transistors 10, 12 to rapidly turn on the opposing complementary pair n-channel transistors 16, 14 during output signal transition, first and second conducting devices 26, 28 are respectively connected to the gates of transistors 14, 16. At the onset of input signal transition from V_(DD) to V₁, conducting device 26 activates to discharge a portion of the capacitive gate charge of transistor 14 allowing transistor 10 to rapidly pull the gate of transistor 16 up to V_(DD) and turn on transistor 16. Similarly, at the onset of an input signal transition from V₁ to V_(DD) conducting device 28 activates to discharge the capacitive gate charge of transistor 16 thereby allowing transistor 12 to rapidly pull the gate of transistor 14 up to V_(DD) and turn on transistor 14. Conducting devices 26, 28 may but do not necessarily need to completely turn off the respective n-channel trasistors 10, 12.

The conducting devices 26, 28 may be connected to any voltage source having an output voltage lower than the potential of the capacitive charge remaining on the gates of the n-channel transistors during an input signal transition. This potential is approximately V_(DD). Since V₂ is typically lower than V_(DD) conducting devices 26, 28 may be connected to the second voltage source supplying V₂. Alternatively, since V₁ is also typically lower than V_(DD) the conducting device 26 may be connected to the signal input 24 and the conducting device 28 connected to the output of the inverter 22.

Since the interval during which the p-channel transistors 10, 12 pull up against the drain of the complementary n-channel transistors 14, 16 is minimized the geometry of the respective transistors in each complementary transistor pair 10, 14 and 12, 16 may be approximately the same. The overall output signal transition speed of the present inventive level shifter is also substantially enhanced. In one embodiment discussed more fully below, a level shifter operating frequency of several megahertz has been achieved. Transient power consumption in the present inventive level shifter may also be minimized by operating the conducting devices 26, 28 for only a brief period to discharge a portion of the capacitive gate charges of the transistors 14, 16 sufficient to substantially decrease the conductivity of the transistors.

The conducting devices 26, 28 may be embodied in the number of different circuits. FIGS. 2-5 show several preferred embodiments of the present inventive level shifter employing different embodiments of the conducting devices 26, 28. In each of these figures the same pairs of complementary p-channel and n-channel metal oxide semiconductor transistors 10, 14 and 12, 16 respectively, and the signal inverter 22 are employed.

In FIG. 2 one preferred embodiment of the present inventive level shifter is shown with capacitors 30, 32 acting as the conducting devices 26, 28. The capacitors 30, 32 are respectively connected across the gates of each transistor pair 10, 14 and 12, 16.

In operation, with an input signal at V_(DD), a node 30a of capacitor 30 which is connected to the gate of transistor 10 and signal input 24 is at V_(DD). A node 30b of capacitor 30 which is connected to the gate of transistor 14 and node 20 is also at V_(DD) (since transistor 12 is on node 20 is therefore at V_(DD)). When the input signal voltage level shifts to V₁, transistor 12 will turn off and both the gate of transistor 14 and capacitor node 30b will float at V_(DD). The capacitor node 30a, however, will be at the input signal voltage level V₁ thus providing a voltage differential across capacitor 30. The value of capacitor 30 may be selected to rapidly drain a quantity of the capacitive gate charge on transistor 14 thereby greatly reducing the conductivity of transistor 14. This allows transistor 10 to quickly pull node 18 and the gate of transistor 16 sufficiently towards to turn on transistor 16. This in turn brings node 20 and the gate of transistor 14 down to V₂ thereby fully turning off transistor 14.

Capacitor 32 acts similarly with respect to transistors 12 and 16. An input signal transition from V₁ back to V_(DD) turns off transistor 10 thereby floating the gate of transistor 16 and a node 32b of capacitor 32 connected to the gate of transistor 16. A node 32a of capacitor 32 connected to the gate of transistor 12, however, will be at V₁ due to inverter 24. The capacitive charge on the gate of transistor 16 will thus be partially drained by capacitor 32 thereby allowing transistor 12 to more quickly pull the gate of transistor 14 up to V₁, thus turning transistor 14 on and turning transistor 16 off.

Use of capacitors 30, 32 as conducting devices 26, 28 can substantially increase the operating frequency of the present inventive level shifter and minimize its transient power consumption. The output signal transition speed of the level shifter, however, is dependent upon the rate at which capacitors 30, 32 drain the transient capacitive gate charges of transistors 14, 16 and, consequently the capacitive values of capacitors 30, 32 themselves. The capacitors 30, 32 may be either fabricated as part of an integrated level shifter circuit or as discrete elements.

In FIGS. 3-5 alternative embodiments of the present inventive level shifter are shown employing n-channel metal oxide semiconductor (MOS) transistors 34, 36 as the conductive devices 26, 28. In each of these embodiments transistors 34, 36 are respectively connected across the gates of transistors 14, 16 and the second voltage source at level V₂ to discharge the transient capacitive gate charge of transistors 14, 16 during output signal transistion. The method of turning the discharging transitors 34, 36 on and off, however, differs in each embodiment.

In the embodiment shown in FIG. 3, two p-channel transistors 38, 40 are used to switch discharging transistor 34 on and off and two p-channel transistors 42, 44 are used to switch discharging transistor 36 on and off. Transistors 38 and 40 are connected together with the source of either transistor connected to the first voltage source at V_(DD) and the drain of the other transistor connected at node 46 to the gate of transistor 36. Similarly, transistors 42 and 44 are connected together with the source of either transistor also connected to the first voltage source and the drain of the other tansistor connected at node 48 to the gate of transistor 36. Switching transistor pairs 38, 40 and 42, 44 thus provide switchable conducting paths between the respective gates of the discharging transistors 32, 36 and the first voltage source at V_(DD).

Two n-channel transistors 50, 52 are respectively connected across nodes 46, 48 and the second voltage source at V₂. Transistors 50, 52 serve as resistive elements to minimize current flow through the switching transistor pairs 38, 40 and 42, 44. The gates of transistors 50, 52 are connected at node 54 to a conventional high impedance constant voltage source which supplies a voltage approximating the threshold voltage levels of transistors 50, 52. Transistors 50, 52 thus provide a high impedance conducting path between the second voltage source at V₂ and the respective switching transistor pairs 38, 40 and 44, 42 connected to the first voltage source at V_(DD). Typically the impedance of transistors 50, 52 is on the order of 1-10 megaohms. High impedance constant voltage sources are well known in the prior art. Current mirrors are a common voltage source of this type.

Transistors 50, 52 could be replaced by any suitable resistive element. Since the entire level shifter of the present invention could be manufactured as a single monolithic circuit, transistors 50, 52 could, for example, be replaced by a pair of integrated circuit thick or thin film resistive elements such as polysilicon load elements.

The operation of the switching transistor pair 38, 40 is controlled by connecting the gate of transistor 40 to the signal input 24 and connecting the gate of transistor 38 to the output of a signal inverter 54. The inverter 54 has an input connected at node 56 to the signal input 24 and provides an inverted signal output varying between the input signal voltage levels V_(DD) and V₁. A capacitive element 58 is connected across the output of inverter 54 and a third voltage source supplying a voltage at V₁. Similarly, the operation of the switching transistor pair 42, 44 is controlled by connecting the gate of transistor 44 to the output of the inverter 22 and connecting the gate of transistor 40 to the output of a singal inverter 60. The inverter 60 has an input connected to the output of inverter 22 and also supplies an inverted output signal varying between V_(DD) and V₁. A capacitive element 62 is similarly connected across the third voltage source at V₁ and the output of inverter 60.

In operation, with an input signal at V_(DD), transistors 10, 16 will be turned off and transistors 12, 14 will be turned on as discussed before. Transistor 40 will be turned off and transistor 38 will be turned on with the gate of tansistor 38 and both sides of capacitor 58 at V₁. With transistor 40 turned off, transistor 34 will also be turned off with its gate pulled towards V₂ by transistor 50. Transistor 42 will be turned on due to inverter 22 and transistor 44 will be turned off with its gate at approximately V_(DD) due to inverter 60. Capacitor 62 will have a differential voltage of approximately V_(DD) minus V₁.

When the input signal shifts from V_(DD) to V₁, transistor 40 turns on and transistor 38 remains on thereby turning transistor 34 on by pulling its gate up towards V_(DD). With transistor 34 on, the capacitive charge on the gate of tansistor 14 is discharged thereby allowing transistor 10 to more rapidly turn on transistor 16 which shifts the output of node 20 to V₂. With the signal input shift from V_(DD) to V₁, the output from inverter 54 shifts from V₁ to V_(DD). Transistor 38, however, will not turn off until inverter 54 has charged up capacitor 58. When transistor 38 is turned off by inverter 54, the voltage at the gate of transistor 34 will drop back towards V₂ thereby turning off transistor 34. The interval during which discharging transistor 34 remains on is thus determined by the charging rate of capacitor 58. The input signal shift from V_(DD) to V₁ will also cause inverter 60 to charge up capacitor 62 and turn on transistor 42. Transistor 44, however, will be turned off due to inverter 22 thus assuring that transistor 36 remains off with its gate pulled towards V₂ by transistor 50.

When the input voltage level shifts from V₁ back to V_(DD), transistor 10 will turn off and transistor 12 will turn on with the gate of transistor 16 potentially left floating at V_(DD). Now however, the output from inverter 22 will turn on transistor 44 and transistor 42 will remain on thereby turning on transistor 36 by pulling its gate up towards V_(DD). The capacitive charge on the gate of transistor 16 will therefore be discharged through transistor 36 allowing transistor 12 to more rapidly turn on transistor 14, thus bringing the output signal voltage level at node 20 back to V_(DD). When the output from inverter 60 has charged up capacitor 62, the gate of transistor 42 will approach V_(DD) thereby turning off both transistor 42 and transistor 36.

Use of transistors 34, 36 to rapidly discharge the respective transient capacitive gate charge on transistors 14, 16 has allowed this embodiment of the present inventive level shifter to operater at relatively high frequencies. For example, level shifters of this inventive embodiment have been observed to operate at frequencies as high as several megahertz. Since transistors 10, 14 (connected across the first voltage source V_(DD) and the respective gates of transistors 16, 14) turn off when discharging transistors 34, 36 turn on, minimal power is consumed during output signal transition.

In the embodiment shown in FIG. 4, transistors 38, 40 and 42, 44 are again used to provide switchable conducting paths between the respective gates of discharging transistors 32, 34 and the first voltage source at V_(DD). Transistors 50, 52 are also employed again as resistive loads across the gates of transistors 32, 36 and the second voltage source at V₂. Inverters 54, 60, however, are respectively replaced by pairs of complementary p-channel and n-channel transistors 64, 66 and 68, 70. The complementary transistors 64, 66 and 68, 70 in each pair are connected together and respectively connected to the first and second voltage sources. Transistors 66, 70 serve the same purpose of providing resistive loads as transistors 50, 52 and could similarly be replaced with conventional integrated circuit or discrete resistive elements.

The gates of transistors 38, 42 are now respectively connected at nodes 72, 74 to the drains of transistors 64, 66 and 68, 70. Transistors 64, 68 have their gates respectively connected to the signal input 24 and the output of the inverter 22. The gates of transistors 66, 70 are connected at node 54 to a high impedance constant voltage source along with transistors 50, 52. A pair of capacitors 76, 78 are respectively connected between the gates of transistors 38, 42 and the second voltage source at V₂.

In operation, with an input signal at V_(DD), transistors 10, 40, 64 and 16 will be off while transistors 12, 44, 68 and 14 will be on. With transistor 64 off, transistor 38 will be on with its gate pulled towards V₂ by transistor 66. With transistor 68 on, transistor 42 will be off with its gate pulled towards V_(DD) by transistor 68. This results in a differential voltage across capacitor 78. When the input signal changes from V_(DD) to V₁, transistors 10, 40 and 64 will turn on while transistors 12, 44 and 68 turn off. With transistors 38 and 40 both on, the gate of transistor 34 will be pulled up towards V_(DD) thereby turning transistor 34 on and discharging a capacitive charge on the now floating gate of transistor 14. The conductivity of transistor 14 will swiftly decrease thereby allowing transistor 10 to rapidly turn on transistor 16 thus pulling the voltage level of signal output node 20 to V₂.

Transistor 38 will remain on until transistor 64 charges up capacitor 72 thereby pulling the gate of transistor 38 towards V_(DD). When transistor 38 turns off transistor 34 also turns off with its gate pulled back towards V₂ by transistor 50. When transistor 68 turns off during the input signal shift from V_(DD) to V₁, the charge on capacitor 74 will drain off through transistor 70 thereby allowing transistor 42 to turn on. Transistor 44, however, will be off thus leaving transistor 36 off with its gate pulled towards V₂ by transistor 52.

When the input signal shifts back to V_(DD) from V₁, transistor 42 will be on due to the draining of capacitor 74 through transistor 70 and transistor 44 will be turned on by inverter 22. The gate of transistor 36 will then be pulled up towards V_(DD) thereby turning on transistor 36 and draining a portion of the capacitive charge on the gate of transistor 16. The conductivity of transistor 16 will swiftly decrease thus allowing transistor 12 to rapidly turn on transistor 14, shifting the output voltage level node at 20 from V₂ back to V_(DD). With transistor 68 now turned on by inverter 22, transistor 42 will be turned off by transistor 68 charging up capacitor 74 and pulling the gate of transistor 42 towards V_(DD). When transistor 42 turns off, transistor 36 will turn off with its gate pulled back towards V₂ by transistor 52.

The embodiment shown in FIG. 5 also employs transistors 34, 36 to respectively drain transient capacitive charges on the gates of transistors 14, 16. In this embodiment, however, a feedback control is provided between the voltage levels at the drains of transistors 14, 16 and the switching of transistors 34, 36 on or off. The p-channel transistor pairs 38, 40 and 42, 44 are again used to provide switchable conducting paths between the respective gates of the discharging transistors 34, 36 and the first voltage source. Similarly, the n-channel transistors 50, 52 are also employed as resistive loads between the secoar bone.

In some cases, it is necessary or advantageous to set up compressive stresses in the longitudinal direction in a tubular bone, for example when treating fractures, or in combination with endoprostheses, in particular hip joint endoprostheses.

Devices of this type in which the tension element has to be fixed in the depth of the tubular bone by an anchoring device to be introduced at an angle into the bone from outside are known. However, the additional operation to introduce the anchoring device laterally from outside the bone is a problem. Moreover, devices in which the anchoring device is introduced into the medullary cavity from its end, and which comprise a multiplicity of mechanically expandable spikes which are intended to anchor themselves on the walls in the depth of the medullary cavity, are known. The disadvantage of devices of this type is the complicated mechanism necessary for expanding the spikes, which is susceptible to faults and whose loadbearing capacity is limited, since it is possible for the spikes to grip adequately only if they engage not only in the spongy substance but also in the cortical substance, but this is doubtful because of the hardness of the cortical substance and the dimensioning of the device which is predetermined by the bone.

The invention has the object of producing a device of the type mentioned in the introduction, which avoids these disadvantages. This is achieved by the characterising features of claim 1, advantageously in combination with the features of one or more dependent claims.

On introduction of the tension rod, the anchoring device, due to its hinged connection to the tension rod, tilts more or less toward the latter, so that the crosssectional dimensions of the device composed of the tension rod and the anchoring device are sufficiently smaller than the diameter of the medullary cavity into which it is to be pushed. When the tension rod is under tensile stress, due to force being exerted from one side, the plate tilts away from the tension rod and is locked against the walls of the medullary cavity. This locking can be promoted by indentations applied to the ends of the plate or, where appropriate, also on its sides.

The anchoring device remains stable in its anchoring position as long as its angle with the wall of the medullary cavity is greater than the angle of friction. Since the coefficient of friction of the sharp-edged anchoring device with respect to the rough cortical substance is very high, this condition allows a very great margin of latitude in the angle of the anchoring device. Moreover, this results in very wide limits for its longitudinal dimension. Thus, an exact adjustment to the diameter of the medullary cavity is unnecessary.

The eccentricity of the connection between the anchoring device and the tension rod needs to be only as large as is necessary to ensure the tilting of the anchoring device in the medullary cavity and thus the desired locking between the walls of the medullary cavity. Furthermore, it should not be considerably greater than is necessary for this purpose, so that the difference, resulting from this, in the stress on the two ends of the anchoring device is as small as possible. The claimed feature that the hinged connection between the anchoring device and the tension rod is provided at one end of the anchoring device should also be interpreted in this sense.

The swivelling axis of the hinge is at right-angles to the longitudinal axes of the tension rod and of the anchoring device. A very simple embodiment of the hinge comprises the tension rod being passed through a hole which is drilled in the anchor and whose diameter is considerably larger than that of the tension rod, the tension rod being thickened on both sides of the drilled hole, the thickening taking the form of, for example, a sphere, as can be produced by a welding bead.

The invention is illustrated in detail below with reference to the drawing, which illustrates an advantageous exemplary embodiment. In this:

FIG. 1 shows a side view of the device,

FIG. 2 shows an end view of the device,

FIG. 3 shows the principle of the anchoring when treating a fracture, and

FIG. 4 shows the use of the device in association with a hip joint endoprosthesis.

The tension rod 1 has two spherical thickenings 2, 3 at one end. Between these, it passes through the hole 4 drilled in the anchoring device 5 which is in the form of a plate, the diameter of the drilled hole being smaller than the diameter of the spherical thickenings 2 and 3. The anchoring device 5 has an oval outline, its shorter transverse axis being smaller than the diameter of the medullary canal, while its longer axis is larger, preferably by a factor of 1.05-1.4, than the diameter of the medullary cavity. The ends have indentations 6 to improve the anchoring to the inner surface of the cortical substance of the bone.

The diameter of the drilled hole 4 is larger than the diameter of the rod 2 to an extent sufficient for the anchoring device on the rod to tilt into a position in which each dimension measured at right-angles to the longitudinal axis of the rod is smaller than the diameter of the medullary cavity.

This latter feature permits the device to be pushed in the longitudinal direction into the medullary cavity 7 of a bone 8, in accordance with FIG. 3, during which the anchoring device is swivelled with respect to the tension rod into the position shown by the dotted line. When a tensile force is subsequently exerted on the tension rod, then the anchoring device tilts into the position illustrated by the full lines, in which position it locks fast onto the inner walls of the cortical substance 8 and thus forms a reliable end support when the parts of the bone, which are shown separated, are tensioned together in the longitudinal direction by means of the tension rod, the other end of which is provided with an end support plate 9 and a nut 10.

FIG. 4 shows an analogous application in association with a hip joint femoral prosthesis 11. The tension rod 1, which is anchored in the femur 12 by means of the anchoring device 5, is passed proximally through a drilled hole 13 in the neck support plate 14 of the prosthesis 11 and is tensioned by means of a nut 15. Thus, the involvement of the medial part of the bone 12 and the transmission of force to the prosthesis can be increased. 

I claim:
 1. Method for anchoring a tubular bone, comprising:(a) inserting into the medullary cavity of said bone an oblong plate having a longitudinal axis greater than the diameter of said medullary cavity and a transverse axis less than said diameter, said oblong plate being mounted to a tension rod through a hinge connection along said longitudinal axis and eccentric with respect to said oblong plate; and (b) applying elongating tension to said tension rod to anchor said oblong plate to the inner surface of said medullary cavity.
 2. Method according to claim 1 in which said oblong plate has one curved edge.
 3. Method according to claim 1 in which said oblong plate is oval in shape.
 4. Method according to claim 1 in which step (b) comprises tilting said oblong plate at said hinge connection to anchor the edges of said oblong plate at each end of said longitudinal axis against the inner surface of said medullary cavity.
 5. Method according to claim 1 in which said oblong plate has serrations along the edges thereof at each end of said longitudinal axis, and step (b) comprises anchoring said serrations against the inner surface of said medullary cavity.
 6. Method according to claim 2 in which said oblong plate has serrations along the edges thereof at each end of said longitudinal axis, and step (b) comprises anchoring said serrations against the inner surface of said medullary cavity.
 7. Method according to claim 3 in which said oblong plate has serrations along the edges thereof at each end of said longitudinal axis, and step (b) comprises anchoring said serrations against the inner surface of said medullary cavity . 